Current Mode Control Type Switching Power Supply Device

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of U.S. patent application Ser. No. 15/999,702, filed Aug. 20, 2018, which is a continuation of U.S. patent application Ser. No. 14/859,676, filed Sep. 21, 2015, now U.S. Pat. No. 10,076,963, which claims priority under 35 U.S.C. § 119(a) on Patent Application No. 2014-194209 filed in Japan on Sep. 24, 2014, Patent Application No. 2014-194211 filed in Japan on Sep. 24, 2014, Patent Application No. 2014-194215 filed in Japan on Sep. 24, 2014, and Patent Application No. 2014-194230 filed in Japan on Sep. 24, 2014, the entire contents of which are hereby incorporated by reference.

BACKGROUND OF THE INVENTION

Field of the Invention

The present invention relates to a current mode control type switching power supply device that can perform a step down operation for stepping down an input voltage.

Description of Related Art

Control methods of switching power supply devices can be roughly divided into a voltage mode control and a current mode control. In general, the current mode control is very effective in view of simplification of phase compensation, fast response, and reduction of the number of external components. An example of the current mode control type switching power supply device is shown in FIG. 14 .

A switching power supply device 100 shown in FIG. 14 senses current flowing in an upper metal oxide semiconductor (MOS) transistor Q 1 so as to perform the current mode control. In accordance with the current mode control, the upper MOS transistor Q 1 and a lower MOS transistor Q 2 are complementarily turned on and off, and an input voltage V IN is converted into a pulse-like switched voltage V SW by this switching operation. Then, the switched voltage V SW is smoothed by an inductor and an output capacitor and is converted into an output voltage V OUT lower than the input voltage V IN .

When the current flowing in the upper MOS transistor Q 1 is sensed so as to perform the current mode control, a fed-back portion of the current corresponds to a difference between the input voltage and the switched voltage (V IN -V SW ), and hence a current sensing circuit generates information of the sensed current with respect to the input voltage V IN . Accordingly, when the current information is transmitted to a slope circuit configured to generate a slope voltage V SLP with respect to an internal source voltage, there occurs a delay time D after the upper MOS transistor Q 1 is turned on until the current information is transmitted to the slope voltage V SLP , as shown in FIG. 15 .

In addition, because the fed-back portion of the current corresponds to the difference between the input voltage and the switched voltage (V IN -V SW ), if noise is added to a leading edge or the like of the switched voltage V SW , the noise is transmitted as it is and is reflected on the slope voltage V SLP .

Further, when a pulse width of the switched voltage V SW is decreased, the above-mentioned delay time and noise become dominant, and there occurs a problem that current feedback cannot be performed.

Note that the current mode control type switching power supply device disclosed in JP-A-2010-220355 also performs the current mode control by sensing current flowing in an upper switching element similarly to the switching power supply device 100 shown in FIG. 14 , and hence has the same problem.

SUMMARY OF THE INVENTION

It is an object of the present invention to provide a current mode control type switching power supply device that can perform current feedback even if a ratio of an output voltage to an input voltage is small.

<First Technical Feature>

Among the current mode control type switching power supply devices disclosed in this specification, the current mode control type switching power supply device having the first technical feature includes a first switch having a first terminal connected to a first application terminal to which an input voltage is applied, a second switch having a first terminal connected to a second terminal of the first switch and a second terminal connected to a second application terminal to which a predetermined voltage lower than the input voltage is applied, a current sensing portion configured to sense current flowing in the second switch, and a controller configured to control the first switch and the second switch in accordance with current sensed by the current sensing portion. The controller includes an accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state, and a reflecting portion configured to start the transmission of the current information accumulated by the accumulating portion before the first switch is changed from the off state to the on state so as to reflect the current information accumulated by the accumulating portion on the slope voltage, and controls the first switch and the second switch in accordance with the slope voltage.

<Second Technical Feature>

Among the current mode control type switching power supply devices disclosed in this specification, the current mode control type switching power supply device having the second technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes a slope voltage generating portion configured to accumulate, during a predetermined period of time while the first switch is in the off state, information of the current sensed by the current sensing portion so as to generate a slope voltage based on the accumulated current information, and controls the first switch and the second switch in accordance with the slope voltage.

<Third Technical Feature>

Among the current mode control type switching power supply devices disclosed in this specification, the current mode control type switching power supply device having the third technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes an accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a constant of time while the first switch is in the off state, and the reflecting portion configured to reflect the current information accumulated by the accumulating portion on the slope voltage, and controls the first switch and the second switch in accordance with the slope voltage.

<Fourth Technical Feature>

Among the current mode control type switching power supply devices disclosed in this specification, the current mode control type switching power supply device having the fourth technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes an accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state, a reflecting portion configured to reflect the current information accumulated by the accumulating portion on the offset voltage of the slope voltage, and a gradient setting portion configured to set a constant slope gradient of the slope voltage, and controls the first switch and the second switch in accordance with the slope voltage.

Meanings and effects of the present invention will become apparent from the description of embodiments given below. However, the embodiments described below are merely examples of the present invention. The present invention and meanings of terms of structural elements are not limited to those shown in the embodiments described below.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a diagram showing an example of a general structure of a first embodiment of a switching power supply device.

FIG. 2 is a diagram showing a structural example of a current sensing circuit and a slope circuit.

FIG. 3 A is a diagram showing a structural example of a voltage current conversion circuit 4 A.

FIG. 3 B is a diagram showing a structural example of a voltage current conversion circuit 5 A.

FIG. 4 A is a timing chart showing an operation example of the switching power supply device.

FIG. 4 B is a timing chart showing a variation of the operation example shown in FIG. 4 A .

FIG. 5 A is a timing chart showing another operation example of the switching power supply device.

FIG. 5 B is a timing chart showing of a variation of the operation example shown in FIG. 5 A .

FIG. 6 A is a timing chart showing still another operation example of the switching power supply device.

FIG. 6 B is a timing chart showing a variation of the operation example shown in FIG. 6 A .

FIG. 7 is a diagram showing of a schematic waveform of a slope voltage having slope gradient on which current information is reflected.

FIG. 8 is a diagram showing a schematic waveform of a slope voltage having a slope offset voltage on which the current information is reflected.

FIG. 9 is a diagram showing another structural example of the current sensing circuit and the slope circuit.

FIG. 10 is a timing chart showing still another operation example of the switching power supply device.

FIG. 11 is a diagram showing a general structural example of a second embodiment of the switching power supply device.

FIG. 12 A is a timing chart showing an example of determination as to a ratio of an output voltage to an input voltage.

FIG. 12 B is a timing chart showing another example of determination as to the ratio of the output voltage to the input voltage.

FIG. 13 is an outside view showing a structural example of a vehicle in which in-vehicle equipment is mounted.

FIG. 14 is a diagram showing an example of a current mode control type switching power supply device.

FIG. 15 is a timing chart showing an operation example of the switching power supply device shown in FIG. 14 .

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

General Structure (First Embodiment)

FIG. 1 is a diagram showing an example of a general structure of a first embodiment of a current mode control type switching power supply device. A switching power supply device 101 of this structural example is a current mode control type switching power supply device that performs a step down operation for stepping down an input voltage and includes a timing control circuit 1 , an upper MOS transistor Q 1 , a lower MOS transistor Q 2 , an inductor L 1 , an output capacitor C 1 , voltage dividing resistors R 1 and R 2 , an error amplifier 2 , a reference voltage source 3 , a current sensing circuit 4 , a slope circuit 5 , a comparator 6 , and an oscillator 7 .

The timing control circuit 1 controls on and off of the upper MOS transistor Q 1 and on and off of the lower MOS transistor Q 2 , and generates a gate signal G 1 of the upper MOS transistor Q 1 and a gate signal G 2 of the lower MOS transistor Q 2 in accordance with a set signal SET and a reset signal RESET.

The upper MOS transistor Q 1 is an N-channel MOS transistor as an example of an upper switch configured to make and break a current path from an input voltage application terminal applied with an input voltage V IN to the inductor L 1 . A drain of the upper MOS transistor Q 1 is connected to the input voltage application terminal applied with the input voltage V IN . A source of the upper MOS transistor Q 1 is connected to a terminal of the inductor and a drain of the lower MOS transistor Q 2 . A gate of the upper MOS transistor Q 1 is provided with the gate signal G 1 from the timing control circuit 1 . The upper MOS transistor Q 1 is turned on when the gate signal G 1 is high level and is turned off when the gate signal G 1 is low level.

The lower MOS transistor Q 2 is an N-channel MOS transistor as an example of a lower switch configured to make and break a current path from a ground terminal to the inductor L 1 . The drain of the lower MOS transistor Q 2 is connected to the terminal of the inductor and the source of the upper MOS transistor Q 1 as described above. A source of the lower MOS transistor Q 2 is connected to the ground terminal. A gate of the lower MOS transistor Q 2 is supplied with a gate signal G 2 from the timing control circuit 1 . The lower MOS transistor Q 2 is turned on when the gate signal G 2 is high level and is turned off when the gate signal G 2 is low level. Note that a diode can be used instead of the lower MOS transistor Q 2 as the lower switch, but in this case, it is necessary to dispose a sense resistor connected in series to the diode so that the current sensing circuit 4 senses a voltage between both ends of the sense resistor.

The upper MOS transistor Q 1 and the lower MOS transistor Q 2 are complementarily turned on and off by control by the timing control circuit 1 . In this way, a pulse-like switched voltage V SW is generated at a connection node between the upper MOS transistor Q 1 and the lower MOS transistor Q 2 . Note that it is preferred to set a dead time in which both the upper MOS transistor Q 1 and the lower MOS transistor Q 2 are off when on/off states of the upper MOS transistor Q 1 and the lower MOS transistor Q 2 are exchanged.

The inductor L 1 and the output capacitor C 1 smooth the pulse-like switched voltage V SW so as to generate an output voltage V OUT and supply the output voltage V OUT to an application terminal of the output voltage V OUT .

The voltage dividing resistors R 1 and R 2 divide the output voltage V OUT so as to generate a feedback voltage V FB .

The error amplifier 2 generates an error signal V ERR corresponding to a difference between the feedback voltage V FB and a reference voltage output from the reference voltage source 3 .

The current sensing circuit 4 senses current flowing in the lower MOS transistor Q 2 on the basis of a drain-source voltage when the lower MOS transistor Q 2 is on, namely a voltage between both ends of an on resistor of the lower MOS transistor Q 2 .

The slope circuit 5 generates and outputs a slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 .

The comparator 6 compares the output voltage of the slope circuit 5 with the error signal V ERR so as to generate the reset signal RESET as a comparison signal. Because a slope voltage V SLP generated by the slope circuit 5 has a fixed period, the reset signal RESET becomes a pulse width modulation (PWM) signal.

The oscillator 7 generates the set signal SET that is a clock signal having a predetermined frequency.

First Generation Example of Slope Voltage

FIG. 2 is a diagram showing a structural example of the current sensing circuit 4 and the slope circuit 5 . In the example shown in FIG. 2 , the current sensing circuit 4 is constituted of the voltage current conversion circuit 4 A. In addition, in the example shown in FIG. 2 , the slope circuit 5 is constituted of switches S 1 to S 3 , capacitors C 2 and C 3 , and a voltage current conversion circuit 5 A.

Each of the voltage current conversion circuits 4 A and 5 A is a circuit driven by an internal source voltage V CC generated in an integrated circuit (IC) including the timing control circuit 1 , the error amplifier 2 , the reference voltage source 3 , the current sensing circuit 4 , the slope circuit 5 , the comparator 6 , and the oscillator 7 .

The voltage current conversion circuit 4 A converts a drain-source voltage of the lower MOS transistor Q 2 into current and outputs the current. When the switch S 1 is on, the capacitor C 2 is charged by output current of the voltage current conversion circuit 4 A. On the other hand, when the switch S 2 is on, the capacitor C 2 is discharged.

The voltage current conversion circuit 5 A converts a charge voltage V CRG of the capacitor C 2 into current and outputs the current. The output current of the voltage current conversion circuit 5 A charges the capacitor C 3 . On the other hand, when the switch S 3 is on, the capacitor C 3 is discharged. A charge voltage of the capacitor C 3 becomes the slope voltage V SLP .

FIGS. 3 A and 3 B are diagrams showing structural examples of the voltage current conversion circuits 4 A and 5 A. In the voltage current conversion circuit shown in FIG. 3 A , a current source 8 supplies current to a current mirror circuit constituted of N-channel MOS transistors Q 3 and Q 4 . If a mirror ratio of the current mirror circuit constituted of the N-channel MOS transistors Q 3 and Q 4 is 1:1, current flowing in a resistor R 4 has a value obtained by dividing the switched voltage V SW by a difference (r 3 −r 4 ) between a resistance value r 3 of a resistor R 3 and a resistance value r 4 of the resistor R 4 . Further, the current mirror circuit constituted of P-channel type MOS transistors Q 5 and Q 6 outputs current corresponding to the current flowing in the resistor R 4 (current corresponding to the switched voltage V SW as the input voltage of the voltage current conversion circuit 4 A) as the output current of the voltage current conversion circuit 4 A. In the voltage current conversion circuit shown in FIG. 3 B , current corresponding to the input voltage of the voltage current conversion circuit flows in a resistor R 5 by a series circuit of the resistor R 5 and a PNP transistor Q 7 , and a voltage corresponding to the input voltage of the voltage current conversion circuit is generated at a connection node between the resistor R 5 and the PNP transistor Q 7 . Further, current corresponding to the voltage at the connection node between the resistor R 5 and the PNP transistor Q 7 (voltage corresponding to the input voltage of the voltage current conversion circuit) flows in a resistor R 6 by a series circuit of an NPN transistor Q 8 and the resistor R 6 . Further, a current mirror circuit constituted of P-channel type MOS transistors Q 9 and Q 10 outputs current corresponding to the current flowing in the resistor R 6 (current corresponding to an input voltage V of the voltage current conversion circuit 5 A) as the output current of the voltage current conversion circuit.

FIG. 4 A is a timing chart showing an operation example of the switching power supply device 101 .

In the example shown in FIG. 4 A , the timing control circuit 1 switches the gate signal G 1 from low level to high level when the set signal SET is switched from low level to high level, and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level. The slope circuit 5 changes on and off of the switches S 1 to S 3 in accordance with an instruction from the timing control circuit 1 .

When the reset signal RESET is switched from low level to high level (at timing t 11 ), the slope circuit 5 maintains the off state of the switch S 1 , changes the switch S 2 from the off state to the on state, and changes the switch S 3 from the off state to the on state. In this way, the capacitors C 2 and C 3 are discharged, and each of the charge voltage V CRG of the capacitor C 2 and the slope voltage V SLP becomes zero.

Then, the slope circuit 5 changes the switch S 2 from the on state to the off state so as to finish discharging the capacitor C 2 . After that, at timing t 12 , the slope circuit 5 changes the switch S 1 from the off state to the on state. The timing t 12 can be, for example, the end timing of the dead time just after the upper MOS transistor Q 1 is switched from the on state to the off state.

Next, at timing t 13 , the slope circuit 5 changes the switch S 1 from the on state to the off state. The timing t 13 can be, for example, the start timing of a dead time just after the lower MOS transistor Q 2 is switched from the on state to the off state.

During the period from the timing t 12 to the timing t 13 , a current path from a voltage current conversion circuit 4 A to the capacitor C 2 is formed by the switch S 1 , and hence information of the current flowing in the lower MOS transistor Q 2 is accumulated in a form of the charge voltage V CRG .

After that, when the set signal SET is switched from low level to high level (at timing t 14 ), the slope circuit 5 changes the switch S 3 from the on state to the off state. During the period from the timing t 14 to the next timing t 11 (while the upper MOS transistor Q 1 is on), the output current of the voltage current conversion circuit 5 A charges the capacitor C 3 , and hence the information of the current flowing in the lower MOS transistor Q 2 during the period from the timing t 12 to the timing t 13 is transmitted and reflected on the slope voltage V SLP .

According to the switching power supply device 101 , the fed-back portion of the current corresponds to a difference (V SW −GND) between the switched voltage V SW and the ground voltage. Accordingly, both the current sensing circuit 4 and the slope circuit 5 can be operated on the basis of the internal source voltage V CC like this generation example of the slope voltage, and hence a delay time that can be generated when the current sensing circuit 4 transmits the current information to the slope circuit 5 can be decreased.

In addition, in this generation example of the slope voltage, because the information of the current flowing in the lower MOS transistor Q 2 is accumulated in a form of the charge voltage V CRG during the period from the timing t 12 to the timing t 13 , even if noise is applied to a leading edge or the like of the switched voltage V SW , the noise is averaged during the period from the timing t 12 to the timing t 13 . In other words, amount of noise per unit time that is transmitted and reflected on the slope voltage V SLP can be reduced.

According to this generation example of the slope voltage, current feedback can be performed even if a ratio of the output voltage V OUT to the input voltage V IN is small (even if a pulse width of the switched voltage V SW is small).

Further, in view of stabilizing control system of the current mode control, it is preferred to dispose a superimposing portion in the slope circuit 5 , so that the superimposing portion generates a voltage (a new slope voltage V SLP ′) in which a sawtooth wave-like or triangle wave-like pseudo slope voltage V S increasing at a constant rate during the period from the timing t 14 to the timing t 11 is superimposed on the slope voltage V SLP , and to output the new slope voltage V SLP ′ as the output voltage of the slope circuit 5 . In this case, as shown in FIG. 4 B , when the slope voltage V SLP ′ exceeds the error signal V ERR , the reset signal RESET is switched from low level to high level.

Second Generation Example of Slope Voltage

Structures of the Current Sensing Circuit 4 and the Slope Circuit 5 are the same as those in the first generation example of the slope voltage described above.

FIG. 5 A is a timing chart showing another operation example of the switching power supply device 101 .

In the example shown in FIG. 5 A , the timing control circuit 1 switches the gate signal G 1 from low level to high level when the set signal SET is switched from high level to low level, and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level. The slope circuit 5 changes on and off of the switches S 1 to S 3 in accordance with an instruction from the timing control circuit 1 .

When the reset signal RESET is switched from low level to high level (at timing t 21 ), the slope circuit 5 maintains the off state of the switch S 1 , changes the switch S 2 from the off state to the on state, and changes the switch S 3 from the off state to the on state. In this way, the capacitors C 2 and C 3 are discharged, so that each of the charge voltage V CRG of the capacitor C 2 and the slope voltage V SLP becomes zero.

Then, the slope circuit 5 changes the switch S 2 from the on state to the off state so as to finish discharging the capacitor C 2 . After that, the slope circuit 5 changes the switch S 1 from the off state to the on state at timing t 22 . The timing of t 22 can be the end timing of the dead time just after the upper MOS transistor Q 1 is switched from the on state to the off state, for example.

Next, at timing t 23 , the slope circuit 5 changes the switch S 1 from the on state to the off state. The timing of t 23 can be the start timing of a dead time just after the lower MOS transistor Q 2 is switched from the on state to the off state, for example.

Because the current path from the voltage current conversion circuit 4 A to the capacitor C 2 is formed by the switch S 1 during the period from the timing t 22 to the timing t 23 , the information of the current flowing in the lower MOS transistor Q 2 is accumulated in a form of the charge voltage V CRG .

After that, when the set signal SET is switched from low level to high level (at timing t 24 ), the slope circuit 5 changes the switch S 3 from the on state to the off state. During the output current of the voltage current conversion circuit 5 A charges the capacitor C 3 during the period from the timing t 24 to the next timing t 21 , the information of the current flowing in the lower MOS transistor Q 2 during the period from the timing t 22 to the timing t 23 is transmitted and reflected on the slope voltage V SLP .

In the first generation example of the slope voltage described above, transmission of the information of the current flowing in the lower MOS transistor Q 2 is started so as to be reflected on the slope voltage V SLP at the same time when the upper MOS transistor Q 1 is switched from the off state to the on state. In contrast, in this generation example of the slope voltage, the transmission of the information of the current flowing in the lower MOS transistor Q 2 is started before the upper MOS transistor Q 1 is switched from the off state to the on state so as to be reflected on the slope voltage V SLP . Accordingly, in this generation example of the slope voltage, the minimum pulse width of the switched voltage V SW that enables the current feedback can be smaller than that in the first generation example of the slope voltage described above.

Further, in view of stabilizing control system of the current mode control, it is preferred to dispose a superimposing portion in the slope circuit 5 , so that the superimposing portion generates a voltage (a new slope voltage V SLP ′) in which a sawtooth wave-like or triangle wave-like pseudo slope voltage V S increasing at a constant rate during the period from the timing t 24 to the timing t 21 is superimposed on the slope voltage V SLP , and to output the new slope voltage V SLP ′ as the output voltage of the slope circuit 5 . In this case, as shown in FIG. 5 B , when the slope voltage V SLP ′ exceeds the error signal V ERR , the reset signal RESET is switched from low level to high level.

Third Generation Example of Slope Voltage

Structures of the current sensing circuit 4 and the slope circuit 5 are the same as those in the first generation example and the second generation example of the slope voltage.

FIG. 6 A is a timing chart showing a still another operation example of the switching power supply device 101 .

In the example shown in FIG. 6 A , the timing control circuit 1 switches the gate signal G 1 from low level to high level when the set signal SET is switched from high level to low level, and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level.

In addition, the timing control circuit 1 switches an internal clock signal CLK from low level to high level when the set signal SET is switched from low level to high level, on the basis of the set signal SET, so as to generate the internal clock signal CLK having a high level period shorter than a high level period of the set signal SET. Note that each high level period of the internal clock signal CLK is a constant period of time in which the current feedback is performed in the third generation example of the slope voltage. Note that it is preferred to adjust each high level period of the internal clock signal CLK so that the internal clock signal CLK is switched from high level to low level before the dead time starts just after the lower MOS transistor Q 2 is switched from the on state to the off state.

Further, when the internal clock signal CLK is switched from low level to high level, regardless of a level changing state of the reset signal RESET, the timing control circuit 1 forces the gate signal G 1 to be low level and the gate signal G 2 to be high level. In this way, when the internal clock signal CLK is switched from low level to high level, the current feedback can be securely started.

The slope circuit 5 changes on and off of the switches S 1 to S 3 in accordance with an instruction from the timing control circuit 1 .

When the reset signal RESET is switched from low level to high level (at timing t 31 ), the slope circuit 5 maintains the off state of the switch S 1 , changes the switch S 2 from the off state to the on state, and changes the switch S 3 from the off state to the on state. In this way, the capacitors C 2 and C 3 are discharged, and each of the charge voltage V CRG of the capacitor C 2 and the slope voltage V SLP becomes zero.

Then, the slope circuit 5 changes the switch S 2 from the on state to the off state so as to finish discharging the capacitor C 2 . After that, the slope circuit 5 changes the switch S 1 from the off state to the on state when the internal clock signal CLK is switched from low level to high level (at timing t 32 ).

Next, when the internal clock signal CLK is switched from high level to low level (at timing t 33 ), the slope circuit 5 changes the switch S 1 from the on state to the off state.

During the period from the timing t 32 to the timing t 33 , namely, during a constant period of time in the high level period of the set signal SET, the switch S 1 forms the current path from the voltage current conversion circuit 4 A to the capacitor C 2 . Accordingly, the voltage current conversion circuit 4 A senses the current flowing in the lower MOS transistor Q 2 , and the information of the current flowing in the lower MOS transistor Q 2 is accumulated in a form of the charge voltage V CRG .

After that, the slope circuit 5 changes the switch S 3 from the on state to the off state at timing t 34 . The timing of t 34 can be the start timing of a dead time just after the lower MOS transistor Q 2 is switched from the on state to the off state, for example. Because the output current of the voltage current conversion circuit 5 A charges the capacitor C 3 during the period from the timing t 34 to the next timing t 31 , the information of the current flowing in the lower MOS transistor Q 2 during the period from the timing t 32 to the timing t 33 is transmitted and reflected on the slope voltage V SLP .

In the first generation example and the second generation example of the slope voltage described above, because an on period of the switch S 1 depends on an on period of the upper MOS transistor Q 1 , the on period of the switch S 1 varies depending on the ratio of the output voltage V OUT to the input voltage V IN of the switching power supply device 101 , and hence there is a tendency that the control system of the current mode control becomes unstable. In contrast, in this generation example of the slope voltage, because the on period of the switch S 1 is a constant period, the control system of the current mode control is stabilized.

In addition, in this generation example of the slope voltage, similarly to the second generation example of the slope voltage described above, the transmission of the information of the current flowing in the lower MOS transistor Q 2 is started before the upper MOS transistor Q 1 is switched from the off state to the on state so as to be reflected on the slope voltage V SLP . Accordingly, in this generation example of the slope voltage, the minimum width of the switched voltage V SW that enables the current feedback can be smaller than that in the first generation example of the slope voltage described above.

Further, although the minimum pulse width of the switched voltage V SW that enables the current feedback is the same as that in the first generation example of the slope voltage described above, it is also possible to modify this generation example of the slope voltage in such a manner that the transmission of the information of the current flowing in the lower MOS transistor Q 2 is started so as to be reflected on the slope voltage V SLP when the upper MOS transistor Q 1 is switched from the off state to the on state.

Further, in view of more stabilizing the control system of the current mode control, it is preferred to dispose a superimposing portion in the slope circuit 5 , so that the superimposing portion generates a voltage (a new slope voltage V SLP ′) in which a sawtooth wave-like or triangle wave-like pseudo slope voltage V S increasing at a constant rate during the period from the timing t 34 to the timing t 31 is superimposed on the slope voltage V SLP , and to output the new slope voltage V SLP ′ as the output voltage of the slope circuit 5 . In this case, as shown in FIG. 6 B , when the slope voltage V SLP ′ exceeds the error signal V ERR , the reset signal RESET is switched from low level to high level.

Fourth Generation Example of Slope Voltage

In the first to third generation examples of the slope voltage described above, the slope voltage is generated having a slope gradient on which the current information is reflected as shown in FIG. 7 . In contrast, in this generation example, the slope voltage is generated having a slope offset voltage on which the current information is reflected as shown in FIG. 8 .

When adopting the first to third generation examples of the slope voltage described above, operating conditions are limited because transfer characteristics (closed loop transfer function) of the control system depends on the input voltage V IN and output load (that is connected to the application terminal of the output voltage V OUT ). In contrast, when adopting this generation example, there is a merit that the operating conditions are not limited because the transfer characteristics (closed loop transfer function) of the control system do not depend on the input voltage V IN and the output load.

Hereinafter, a relationship among the transfer characteristics of the control system described above, the input voltage V IN , and the output load is described below in detail.

Case of Adopting First to Third Generation Examples of the Slope Voltage

The relationship of the following equation (1) holds between an on duty D of the upper MOS transistor Q 1 and a value V C of the error signal V ERR output from the error amplifier 2 . Note that S E denotes a slope gradient (fixed value) of the pseudo slope voltage V S , S N denotes a slope gradient on which the information of the current flowing in the lower MOS transistor Q 2 is reflected, and T denotes a coefficient such that the maximum value of D becomes one.

D = ⁢ V C ( S N + S E ) · T = ⁢ ( S N + S E ) · T · V OUT V IN ( S N + S E ) · T ( 1 )

Here, when the value V C of the error signal V ERR output from the error amplifier 2 varies by ΔV C , the on duty D of the upper MOS transistor Q 1 varies by ΔD, and hence the following equation (2) is satisfied. Note that S N ′ denotes the slope gradient on which the information of the current flowing in the lower MOS transistor Q 2 is reflected.

D + Δ ⁢ ⁢ D = ⁢ V C + Δ ⁢ V C ( S N ′ + S E ) · T = ⁢ ( S N + S E ) · T · V OUT V IN + Δ ⁢ V C ( S N ′ + S E ) · T ( 2 )

In accordance with the above-mentioned equation (1) and equation (2), ΔD is expressed by the following equation (3).

Δ ⁢ D = ( S N - S N ′ ) · T · V OUT V IN + Δ ⁢ V C ( S E + S N ' ) · T ( 3 )

Here, because S N is expressed by the following equation (4), the following equation (5) is satisfied. Note that t P denotes the accumulation time of the information of the current flowing in the lower MOS transistor Q 2 , and Tour denotes the output current supplied to the output load. When the value V C of the error signal V ERR output from the error amplifier 2 varies by ΔV C , the output current I OUT varies by ΔI OUT .

S N = ∫ 0 t P ⁢ A ⁢ ⁢ I OUT ⁢ dt ( 4 ) S N ′ - S N = ⁢ ∫ 0 t P ⁢ A ⁡ ( I OUT + Δ ⁢ I ) ⁢ d ⁢ t - ∫ 0 t P ⁢ A ⁢ ⁢ I OUT ⁢ dt = ⁢ A · Δ ⁢ ⁢ I · t P ( 5 )

Here, ΔI is expressed by the following equation (6), and ΔV OUT is expressed by the following equation (7). Note that G DV(S) is a parameter for shaping the switched voltage V SW into the output voltage V OUT .

Δ ⁢ I = Δ ⁢ ⁢ V OUT Z OUT ( 6 ) Δ ⁢ ⁢ V OUT = V IN · Δ ⁢ ⁢ D · G DV ⁡ ( S ) ( 7 )

The above-mentioned equation (6) and equation (7) are substituted into the above-mentioned equation (3) and equation (5), and the equations are organized. Then, the following equation (8) is derived.

Δ ⁢ D Δ ⁢ V C = 1 ( S E + S N ′ ) ⁢ T + A ⁢ V OUT · t F ⁢ T Z OUT ⁢ G DV ⁡ ( S ) ( 8 )

Using the above-mentioned equation (8), a ratio of ΔV OUT to ΔV C is expressed by the following equation (9).

Δ ⁢ V OUT Δ ⁢ V C = ⁢ Δ ⁢ D Δ ⁢ V C · Δ ⁢ V OUT Δ ⁢ D = ⁢ V IN · G DV ⁡ ( S ) ( S E + S N ′ ) ⁢ T + A ⁢ V OUT · t F ⁢ T Z OUT ⁢ G DV ⁡ ( S ) = ⁢ V I ⁢ N · G D ⁢ V ⁡ ( S ) ( S E + S N ′ ) ⁢ T + S N · V OUT ⁢ T Z OUT · I OUT ⁢ G D ⁢ V ⁡ ( S ) ( 9 )

As understood from the above-mentioned equation (9), when the input voltage V IN increases, a voltage gain is increased. When the output current I OUT increases, the G DV(S) of the denominator and the numerator are hardly cancelled by each other, and hence it becomes difficult to perform the current feedback. In other words, the transfer characteristics (closed loop transfer function) of the control system depend on the input voltage V IN and the output load.

Case of Adopting this Generation Example of the Slope Voltage

Similarly to the case of adopting the first to third generation examples of the slope voltage, the transfer characteristics of the control system are considered, and the following equation (12) is derived from the following equation (10). Note that R S denotes a parameter indicating how largely the current information is reflected as an offset voltage on the slope voltage and is expressed by the following equation (11).

Δ ⁢ D = Δ ⁢ V C - R S · Δ ⁢ ⁢ I S E · T ( 10 ) R S = V SLP I OUT ( 11 ) Δ ⁢ V OUT Δ ⁢ ⁢ V C = V IN · G DV ⁡ ( s ) S E · T + R S Z OUT ⁢ V IN ⁢ G DV ⁡ ( s ) ( 12 )

Here, the following equation (14) is satisfied when the condition of the following equation (13) is set.

S E · T ⁢ ⁢ << R S Z OUT ⁢ V IN ⁢ G DV ⁡ ( s ) ( 13 ) Δ ⁢ ⁢ V OUT Δ ⁢ V C = Z OUT R S ( 14 )

As understood from the above-mentioned equation (14), the transfer characteristics of the control system (closed loop transfer function) does not depend on the input voltage V IN and the output load.

Details of this Generation Example

Next, details of this generation example are described. The current sensing circuit 4 and the slope circuit 5 have the structure shown in FIG. 9 , and the switching power supply device 101 operates as shown in FIG. 10 .

In the example shown in FIG. 9 , the current sensing circuit 4 is constituted of the voltage current conversion circuit 4 A. In addition, in the example shown in FIG. 9 , the slope circuit 5 is constituted of switches S 1 , S 2 , and S 4 , the capacitor C 2 , and the constant current source 9 . Note that it is preferred that a value of the constant current output from the constant current source 9 be adjustable.

Each of the voltage current conversion circuit 4 A and the constant current source 9 is a circuit driven by the internal source voltage V CC generated in an integrated circuit (IC) including the timing control circuit 1 , the error amplifier 2 , the reference voltage source 3 , the current sensing circuit 4 , the slope circuit 5 , the comparator 6 , and the oscillator 7 .

The voltage current conversion circuit 4 A converts the drain-source voltage of the lower MOS transistor Q 2 into current and outputs the current. When the switch S 1 is on, the capacitor C 2 is charged by the output current of the voltage current conversion circuit 4 A. When the switch S 4 is on, the capacitor C 2 is charged by the output current of the constant current source 9 . On the other hand, when the switch S 2 is on, the capacitor C 2 is discharged. The charge voltage of the capacitor C 2 becomes the slope voltage V SLP .

In the example shown in FIG. 10 , the timing control circuit 1 switches the gate signal G 1 from low level to high level when the set signal SET is switched from high level to low level, and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level.

In addition, the timing control circuit 1 is switched the internal clock signal CLK from low level to high level when the set signal SET is switched from low level to high level on the basis of the set signal SET, so as to generate the internal clock signal CLK having a high level period shorter than the high level period of the set signal SET. Note that each high level period of the internal clock signal CLK is a constant period of time during which the current feedback is performed in the fourth generation example of the slope voltage. Note that each high level period of the internal clock signal CLK should be adjusted so that the internal clock signal CLK is switched from high level to low level before the dead time starts just after the lower MOS transistor Q 2 is switched from the on state to the off state.

Further, when the internal clock signal CLK is switched from low level to high level, regardless of a level changing state of the reset signal RESET, the timing control circuit 1 forces the gate signal G 1 to be low level and the gate signal G 2 to be high level. In this way, when the internal clock signal CLK is switched from low level to high level, the current feedback can be securely started.

The slope circuit 5 changes on and off of the switches S 1 , S 2 , and S 4 in accordance with an instruction from the timing control circuit 1 .

When the reset signal RESET is switched from low level to high level (at timing t 41 ), the slope circuit 5 maintains the off state of the switch S 1 , changes the switch S 2 from the off state to the on state, and changes the switch S 4 from the on state to the off state. In this way, the capacitor C 2 is discharged, and the slope voltage V SLP as the charge voltage of the capacitor C 2 becomes zero.

Then, the slope circuit 5 changes the switch S 2 from the on state to the off state so as to finish discharging the capacitor C 2 . After that, the slope circuit 5 changes the switch S 1 from the off state to the on state when the internal clock signal CLK is switched from low level to high level (at timing t 42 ).

Next, when the internal clock signal CLK is switched from high level to low level (at timing t 43 ), the slope circuit 5 changes the switch S 1 from the on state to the off state.

During the period from the timing t 42 to the timing t 43 , the switch S 1 forms the current path from the voltage current conversion circuit 4 A to the capacitor C 2 . Accordingly, the information of the current flowing in the lower MOS transistor Q 2 is accumulated in a form of the charge voltage of the capacitor C 2 .

Next, when the set signal SET is switched from high level to low level (at timing t 44 ), the slope circuit 5 changes the switch S 4 from the off state to the on state. During the period from the timing t 44 to the next timing t 41 , the output current of the constant current source 9 charges the capacitor C 2 . In this way, the slope voltage V SLP as the charge voltage of the capacitor C 2 becomes a voltage in which a voltage increasing at a constant ratio corresponding to the output current of the constant current source 9 (a gradient corresponding to the output current of the constant current source 9 ) is superimposed on the offset voltage on which the information of the current flowing in the lower MOS transistor Q 2 is reflected. Further, the slope voltage V SLP as the charge voltage of the capacitor C 2 becomes an output signal of the slope circuit 5 .

In this generation example, the slope voltage V SLP having the slope offset voltage on which the information of the current flowing in the lower MOS transistor Q 2 is reflected is generated. Accordingly, the transfer characteristics (closed loop transfer function) of the control system do not depend on the input voltage V IN and the output load. Accordingly, the operating condition of the switching power supply device 101 is not limited.

In addition, in this generation example, similarly to the second generation example of the slope voltage described above, the transmission of the information of the current flowing in the lower MOS transistor Q 2 is started before the upper MOS transistor Q 1 is switched from the off state to the on state so as to be reflected on the slope voltage V SLP . Accordingly, in this generation example of the slope voltage, the minimum pulse width of the switched voltage V SW that enables the current feedback can be smaller than that of the first generation example of the slope voltage described above.

In addition, in this generation example, similarly to the third generation example of the slope voltage described above, the on period of the switch S 1 is a constant period of time. Accordingly, the control system of the current mode control is stabilized.

General Structure (Second Embodiment)

FIG. 11 is a diagram showing an example of a general structure of a second embodiment of the current mode control type switching power supply device. A switching power supply device 102 of this structural example has a structure in which a current sensing circuit 10 is added to the switching power supply device 101 .

The current sensing circuit 10 senses the current flowing in the upper MOS transistor Q 1 on the basis of the drain-source voltage in the on state of the upper MOS transistor Q 1 , namely the voltage between both ends of the on resistance of the upper MOS transistor Q 1 .

As described above in the first embodiment, the slope circuit 5 generates and outputs the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 . In this way, even if the ratio of the output voltage V OUT to the input voltage V IN is small (even if the switched voltage V SW has a small pulse width), the current feedback can be performed. However, in the form in which the slope circuit 5 generates and outputs the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 , when the pulse width of the switched voltage V SW becomes large, the period of time during which the current flowing in the lower MOS transistor Q 2 can be sensed (while the lower MOS transistor Q 2 is on) is decreased, and hence the current feedback may not be performed. In contrast, in the form in which the slope voltage corresponding to the current flowing in the upper MOS transistor Q 1 is generated so as to perform the current mode control like the conventional technique, when the pulse width of the switched voltage V SW becomes large, the period of time during which the current flowing in the upper MOS transistor Q 1 can be sensed (a period of time while the upper MOS transistor Q 1 is on) is increased, and hence there is no possibility that the current feedback cannot be performed.

Thus, in accordance with an instruction from the timing control circuit 1 , the slope circuit 5 of this embodiment generates and outputs the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 if the ratio of the output voltage to the input voltage (V OUT /V IN ) of the switching power supply device 102 is 50% or less, while it generates and outputs the slope voltage corresponding to the current flowing in the upper MOS transistor Q 1 sensed by the current sensing circuit 10 if V OUT /V IN is more than 50%. In this way, the current feedback can be performed not only in the case where the pulse width of the switched voltage V SW is decreased but also in the case where the pulse width of the switched voltage V SW is increased.

The generation of the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 should be the same as that in each of the generation examples described above in the first embodiment, for example. In addition, the generation of the slope voltage corresponding to the current flowing in the upper MOS transistor Q 1 sensed by the current sensing circuit 10 is known technique, and description thereof is omitted.

FIG. 12 A is a timing chart showing an example of determination whether or not V OUT /V IN is 50% or less. This determination is performed by the timing control circuit 1 that switches the gate signal G 1 from low level to high level when the set signal SET is switched from low level to high level and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level.

The timing control circuit 1 generates a divided clock signal DIV based on the set signal SET. The divided clock signal DIV is a half-divided signal of the set signal SET in which the switch timing from low level to high level is the same as that of the set signal SET.

In addition, the timing control circuit 1 generates a sense clock signal DET based on the set signal SET and the divided clock signal DIV. The sense clock signal DET has the same switch timing from low level to high level as the set signal SET and the divided clock signal DIV, and is switched from high level to low level at timing when the divided clock signal DIV is switched from low level to high level and the set signal SET is not switched from low level to high level.

Further, the timing control circuit 1 determines that the V OUT /V IN is more than 50% if the gate signal G 1 is high level when the sense clock signal DET is switched from high level to low level (in this case, the switched voltage V SW is high level), and determines that the V OUT /V IN is 50% or less if the gate signal G 1 is low level when the sense clock signal DET is switched from high level to low level (in this case, the switched voltage V SW is low level).

FIG. 12 B is a timing chart showing another example of determination whether or not V OUT /V IN is 50% or less. This determination is performed by the timing control circuit 1 that switches the gate signal G 1 from low level to high level when the set signal SET is switched from high level to low level, and switches the gate signal G 1 from high level to low level when the reset signal RESET is switched from low level to high level.

The timing control circuit 1 generates the divided clock signal DIV based on the set signal SET. The divided clock signal DIV is a half-divided signal of the set signal SET and has the same switch timing from high level to low level as the set signal SET.

In addition, the timing control circuit 1 generates the sense clock signal DET based on the set signal SET and the divided clock signal DIV. The sense clock signal DET has the switch timing from low level to high level that is the same as the switch timing of the set signal SET and the divided clock signal DIV from high level to low level, and is switched from high level to low level at timing when the divided clock signal DIV is switched from high level to low level and the set signal SET is not switched from high level to low level.

Further, the timing control circuit 1 determines that V OUT /V IN is more than 50% if the gate signal G 1 is high level when the sense clock signal DET is switched from high level to low level (in this case, the switched voltage V SW is high level), and determines that V OUT /V IN is 50% or less if the gate signal G 1 is low level when the sense clock signal DET is switched from high level to low level (in this case, the switched voltage V SW is low level).

In the above description, the slope circuit 5 outputs the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 if V OUT /V IN is 50% or less. However, 50% is merely an example, and another value may be adopted.

Further in the above description, the slope circuit 5 outputs the slope voltage corresponding to the current flowing in the upper MOS transistor Q 1 sensed by the current sensing circuit 10 if V OUT /V IN is more than 50%. It is possible not to perform the current mode control if V OUT /V IN is more than a predetermined value so as to avoid that the current feedback cannot be performed when the pulse width of the switched voltage V SW is increased. For instance, it is possible to adopt the following structure. The slope circuit 5 generates the pseudo slope voltage. If V OUT /V IN is the predetermined value or smaller, the slope circuit 5 outputs a voltage in which the pseudo slope voltage is superimposed on the slope voltage corresponding to the current flowing in the lower MOS transistor Q 2 sensed by the current sensing circuit 4 (a new slope voltage) as the output voltage of the slope circuit 5 . If V OUT /V IN is larger than the predetermined value, the slope circuit 5 outputs the pseudo slope voltage as the output voltage of the slope circuit 5 .

<Applications>

Next, there is described an application example of the switching power supply device 101 described above. FIG. 13 is an outside view showing a structural example of a vehicle in which in-vehicle equipment is mounted. A vehicle X of this structural example includes in-vehicle equipment X 11 to X 17 and a battery (not shown) configured to supply electric power to the in-vehicle equipment X 11 to X 17 .

The in-vehicle equipment X 11 is an engine control unit configured to perform control related to engine (such as injection control, electronic throttle control, idling control, oxygen sensor heater control, and automatic cruise control).

The in-vehicle equipment X 12 is a lamp control unit configured to control on and off of a high intensity discharged lamp (HID), a daytime running lamp (DRL) and the like.

The in-vehicle equipment X 13 is a transmission control unit configured to perform control related to transmission.

The in-vehicle equipment X 14 is a body control unit configured to perform control related to movement of the vehicle X (such as anti-lock brake system (ABS) control, electric power steering (EPS) control, and electronic suspension control).

The in-vehicle equipment X 15 is a security control unit configured to perform control for driving a door lock, an anti-theft alarm, and the like.

The in-vehicle equipment X 16 is electronic equipment mounted in the vehicle X before shipping, as standard equipment or manufacturer optional equipment, such as wipers, electric door mirrors, power windows, electric sunroof, an electric sheet, and an air conditioner.

The in-vehicle equipment X 17 is electronic equipment mounted in the vehicle X by user's intention, such as in-vehicle audio/visual (A/V) equipment, a car navigation system, and an electronic toll collection (ETC) system.

Note that the switching power supply device 101 described above can be incorporated in any one of the in-vehicle equipment X 11 to X 17 described above.

Another Variation Example

Note that the structure of the present invention can be variously modified from the embodiment described above within the scope of the invention without deviating from the spirit thereof.

For instance, the step-down type switching power supply device is exemplified in the embodiment described above, but applications of the present invention are not limited to this. The present invention can be applied also to a step-up/down type switching power supply device that can perform not only the step down operation but also a step up operation.

In this way, the embodiment described above is merely an example in every aspect and should not be interpreted as a limitation. The technical scope of the present invention should be defined not by the description of the embodiment described above but by the claims, which should be interpreted to include all modifications belonging to meanings and ranges equivalent to the claims.

SUMMARY

(First Technical Feature)

Among the current mode control type switching power supply devices described above, the current mode control type switching power supply device having the first technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes an accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state, and a reflecting portion configured to start transmission of the current information accumulated by the accumulating portion before the first switch is changed from the off state to the on state so as to reflect the current information accumulated by the accumulating portion on the slope voltage, and controls the first switch and the second switch in accordance with the slope voltage (Structure 1-1).

In addition, in the current mode control type switching power supply device having Structure 1-1 described above, the accumulating portion and the reflecting portion may be circuits driven by the same source voltage (Structure 1-2).

In addition, in the current mode control type switching power supply device having Structure 1-1 or Structure 1-2, the current sensing portion may be the voltage current conversion circuit configured to convert the voltage corresponding to the current flowing in the second switch into current, the accumulating portion may include the capacitor to be charged by the output current of the voltage current conversion circuit, and the reflecting portion may reflect the charge voltage of the capacitor on the slope voltage (Structure 1-3).

In addition, in the current mode control type switching power supply device having Structure 1-3 described above, the accumulating portion may further include a charging switch configured to make and break the current path from the output terminal of the voltage current conversion circuit to the capacitor (Structure 1-4).

In addition, in the current mode control type switching power supply device having Structure 1-4 described above, the accumulating portion may change the charging switch from the off state to the on state at the end timing of the dead time just after the first switch is changed from the on state to the off state, and may change the charging switch from the on state to the off state at a start timing of a dead time just after the second switch is changed from the on state to the off state (Structure 1-5).

In addition, in the current mode control type switching power supply device having any one of Structures 1-3 to 1-5 described above, the accumulating portion may have a resetting portion configured to discharge the capacitor so as to reset the charge voltage of the capacitor (Structure 1-6).

In addition, in the current mode control type switching power supply device having any one of Structures 1-1 to 1-6 described above, the controller may include the error amplifier configured to generate an error signal corresponding to a difference between a voltage corresponding to the output voltage of the current mode control type switching power supply device and a reference voltage, the comparator configured to compare the slope voltage with the error signal so as to generate the reset signal as the comparison signal, the oscillator configured to generate the set signal as the clock signal of a predetermined frequency, and the timing control circuit configured to control on and off of the first switch and on and off of the second switch in accordance with the set signal and the reset signal (Structure 1-7).

In addition, in the current mode control type switching power supply device having any one of Structures 1-1 to 1-7 described above, the second switch may be a MOS transistor, and the current sensing portion may sense the current flowing in the second switch by using a voltage between both ends of the on resistor of the MOS transistor (Structure 1-8).

In addition, among the in-vehicle equipment disclosed in this specification, the in-vehicle equipment having the first technical feature includes the current mode control type switching power supply device having any one of Structures 1-1 to 1-8 (Structure 1-9).

In addition, among the vehicles disclosed in this specification, the vehicle having the first technical feature includes the in-vehicle equipment having Structure 1-9 and a battery configured to supply electric power to the in-vehicle equipment (Structure 1-10).

(Second Technical Feature)

Among the current mode control type switching power supply devices described above, the current mode control type switching power supply device having the second technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes a slope voltage generating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state so as to generate the slope voltage based on the accumulated current information, and controls the first switch and the second switch in accordance with the slope voltage (Structure 2-1).

In addition, in the current mode control type switching power supply device having Structure 2-1 described above, the current sensing portion may be the voltage current conversion circuit configured to convert the voltage corresponding to the current flowing in the second switch into current, and the slope voltage generating portion may include the capacitor to be charged by the output current of the voltage current conversion circuit (Structure 2-2).

In addition, in the current mode control type switching power supply device having Structure 2-2 described above, the slope voltage generating portion may further include a charging switch configured to make and break the current path from the output terminal of the voltage current conversion circuit to the capacitor (Structure 2-3).

In addition, in the current mode control type switching power supply device having Structure 2-2 or 2-3 described above, the slope voltage generating portion may include the resetting portion configured to discharge the capacitor so as to reset the charge voltage of the capacitor (Structure 2-4).

In addition, in the current mode control type switching power supply device having any one of Structures 2-1 to 2-4 described above, the controller may include the error amplifier configured to generate the error signal corresponding to the difference between the voltage corresponding to the output voltage of the current mode control type switching power supply device and the reference voltage, the comparator configured to compare the slope voltage with the error signal so as to generate the reset signal as the comparison signal, the oscillator configured to generate the set signal as the clock signal of the predetermined frequency, and the timing control circuit configured to control on and off of the first switch and on and off of the second switch in accordance with the set signal and the reset signal (Structure 2-5).

In addition, in the current mode control type switching power supply device having any one of Structures 2-1 to 2-5, the second switch may be a MOS transistor, and the current sensing portion may sense the current flowing in the second switch by using the voltage between both ends of the on resistor of the MOS transistor (Structure 2-6).

In addition, among the in-vehicle equipment disclosed in this specification, the in-vehicle equipment having the second technical feature includes the current mode control type switching power supply device having any one of Structures 2-1 to 2-6 (Structure 2-7).

In addition, among the vehicles disclosed in this specification, the vehicle having the second technical feature includes the in-vehicle equipment having Structure 2-7 and a battery configured to supply electric power to the in-vehicle equipment (Structure 2-8).

(Third Technical Feature)

Among the current mode control type switching power supply devices described above, the current mode control type switching power supply device having the third technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes the accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a constant period of time while the first switch is in the off state, and the reflecting portion configured to reflect the current information accumulated by the accumulating portion on the slope voltage, and controls the first switch and the second switch in accordance with the slope voltage (Structure 3-1).

In addition, in the current mode control type switching power supply device having Structure 3-1 described above, the controller includes the error amplifier configured to generate the error signal corresponding to a difference between the voltage corresponding to the output voltage of the current mode control type switching power supply device and the reference voltage, the comparator configured to compare the slope voltage with the error signal so as to generate the reset signal as the comparison signal, the oscillator configured to generate the set signal as the clock signal of a predetermined frequency, and the timing control circuit configured to control on and off of the first switch and on and off of the second switch in accordance with the set signal and the reset signal, and the constant period of time is set in the high level period of the set signal (Structure 3-2).

In addition, in the current mode control type switching power supply device having Structure 3-2 described above, the timing control circuit turns on the first switch when the set signal is switched from high level to low level, turns off the first switch when the reset signal is switched from low level to high level, and forcibly turns off the first switch and turns on the second switch regardless of the level changing state of the reset signal when the set signal is switched from low level to high level (Structure 3-3).

In addition, in the current mode control type switching power supply device having any one of Structures 3-1 to 3-3 described above, the accumulating portion and the reflecting portion may be circuits driven by the same source voltage (Structure 3-4).

In addition, in the current mode control type switching power supply device having any one of Structures 3-1 to 3-4 described above, the current sensing portion may be the voltage current conversion circuit configured to convert the voltage corresponding to the current flowing in the second switch into current, the accumulating portion may include the capacitor to be charged by the output current of the voltage current conversion circuit, and the reflecting portion reflects the charge voltage of the capacitor on the slope voltage (Structure 3-5).

In addition, in the current mode control type switching power supply device having Structure 3-5 described above, the accumulating portion may further include the charging switch configured to make and break the current path from the output terminal of the voltage current conversion circuit to the capacitor (Structure 3-6).

In addition, in the current mode control type switching power supply device having Structure 3-5 or 3-6 described above, the accumulating portion may include the resetting portion configured to discharge the capacitor so as to reset the charge voltage of the capacitor (Structure 3-7).

In addition, in the current mode control type switching power supply device having any one of Structures 3-1 to 3-7 described above, the reflecting portion may start the transmission of the current information accumulated by the accumulating portion before the first switch is changed from the off state to the on state so as to reflect the current information accumulated by the accumulating portion on the slope voltage (Structure 3-8).

In addition, in the current mode control type switching power supply device having any one of Structures 3-1 to 3-8 described above, the second switch may be a MOS transistor, and the current sensing portion may sense the current flowing in the second switch by using the voltage between both ends of the on resistor of the MOS transistor (Structure 3-9).

In addition, among the in-vehicle equipment disclosed in this specification, the in-vehicle equipment having the third technical feature may include the current mode control type switching power supply device having any one of Structures 3-1 to 3-9 (Structure 3-10).

In addition, among the vehicles disclosed in this specification, the vehicle having the third technical feature may include the in-vehicle equipment of Structure 3-10 and a battery configured to supply electric power to the in-vehicle equipment (Structure 3-11).

(Fourth Technical Feature)

Among the current mode control type switching power supply devices described above, the current mode control type switching power supply device having the fourth technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch in accordance with the current sensed by the current sensing portion. The controller includes the accumulating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state, the reflecting portion configured to reflect the current information accumulated by the accumulating portion on the offset voltage of the slope voltage, and a gradient setting portion configured to set the slope gradient of the slope voltage to a constant value, and controls the first switch and the second switch in accordance with the slope voltage (Structures 4-1).

In addition, in the current mode control type switching power supply device having Structure 4-1 described above, the predetermined period of time may be a constant period of time (Structures 4-2).

In addition, in the current mode control type switching power supply device having Structure 4-1 or 4-2 described above, the reflecting portion may start the transmission of the current information accumulated by the accumulating portion before the first switch is changed from the off state to the on state so as to reflect the current information accumulated by the accumulating portion on the offset voltage of the slope voltage (Structures 4-3).

In addition, in the current mode control type switching power supply device having any one of Structures 4-1 to 4-3 described above, the current sensing portion may be the voltage current conversion circuit configured to convert the voltage corresponding to the current flowing in the second switch into current, and the accumulating portion and the reflecting portion share the capacitor to be charged by the output current of the voltage current conversion circuit (Structures 4-4).

In addition, in the current mode control type switching power supply device having Structure 4-4 described above, the gradient setting portion may include the constant current source, and a switch for the slope configured to make and break the current path from the constant current source to the capacitor (Structures 4-5).

In addition, in the current mode control type switching power supply device having Structure 4-4 or 4-5 described above, the accumulating portion may further include the charging switch configured to make and break the current path from the output terminal of the voltage current conversion circuit to the capacitor (Structures 4-6).

In addition, in the current mode control type switching power supply device having any one of Structures 4-4 to 4-6 described above, the accumulating portion may include the resetting portion configured to discharge the capacitor so as to reset the charge voltage of the capacitor (Structures 4-7).

In addition, in the current mode control type switching power supply device having any one of Structures 4-1 to 4-7 described above, the controller may include the error amplifier configured to generate the error signal corresponding to the difference between the voltage corresponding to the output voltage and the reference voltage, the comparator configured to compare the slope voltage with the error signal so as to generate the reset signal as the comparison signal, the oscillator configured to generate the set signal as the clock signal of a predetermined frequency, and the timing control circuit configured to control on and off of the first switch and on and off of the second switch in accordance with the set signal and the reset signal (Structures 4-8).

In addition, in the current mode control type switching power supply device having any one of Structures 4-1 to 4-8 described above, the second switch is a MOS transistor, the current sensing portion senses the current flowing in the second switch by using the voltage between both ends of the on resistor of the MOS transistor (Structures 4-9).

In addition, among the in-vehicle equipment disclosed in this specification, the in-vehicle equipment having the fourth technical feature includes the current mode control type switching power supply device having any one of Structures 4-1 to 4-9 (Structure 4-10).

In addition, among the vehicles disclosed in this specification, the vehicle having the fourth technical feature includes the in-vehicle equipment having Structure 4-10 and a battery configured to supply electric power to the in-vehicle equipment (Structure 4-11).

(Fifth Technical Feature)

Among the current mode control type switching power supply devices described above, the current mode control type switching power supply device having the fifth technical feature includes the first switch having the first terminal connected to the first application terminal to which the input voltage is applied, the second switch having the first terminal connected to the second terminal of the first switch and the second terminal connected to the second application terminal to which a predetermined voltage lower than the input voltage is applied, the current sensing portion configured to sense current flowing in the second switch, and the controller configured to control the first switch and the second switch. If the ratio of the output voltage to the input voltage is a predetermined value or lower, the controller controls the first switch and the second switch in accordance with the current sensed by the current sensing portion. If the ratio of the output voltage to the input voltage is higher than the predetermined value, the controller controls the first switch and the second switch independently of the current sensed by the current sensing portion (Structure 5-1).

In addition, the current mode control type switching power supply device having Structure 5-1 described above may further include a current sensing portion for the first switch configured to sense current flowing in the first switch, and the controller may control the first switch and the second switch in accordance with the current sensed by the current sensing portion for the first switch if the ratio of the output voltage to the input voltage is higher than the predetermined value (Structure 5-2).

In addition, in the current mode control type switching power supply device having Structure 5-1 or 5-2 described above, the controller may include the slope voltage generating portion configured to accumulate information of the current sensed by the current sensing portion during a predetermined period of time while the first switch is in the off state so as to generate the slope voltage based on the accumulated current information if the ratio of the output voltage to the input voltage is a predetermined value or lower, and may control the first switch and the second switch in accordance with the slope voltage if the ratio of the output voltage to the input voltage is a predetermined value or lower (Structure 5-3).

In addition, in the current mode control type switching power supply device having Structure 5-3 described above, the current sensing portion may be the voltage current conversion circuit configured to convert the voltage corresponding to the current flowing in the second switch into current, and the slope voltage generating portion may include the capacitor to be charged by the output current of the voltage current conversion circuit (Structure 5-4).

In addition, in the current mode control type switching power supply device having Structure 5-4 described above, the slope voltage generating portion may further include the charging switch configured to make and break the current path from the output terminal of the voltage current conversion circuit to the capacitor (Structure 5-5).

In addition, in the current mode control type switching power supply device having Structure 5-4 or 5-5 described above, the slope voltage generating portion may include the resetting portion configured to discharge the capacitor so as to reset the charge voltage of the capacitor (Structure 5-6).

In addition, in the current mode control type switching power supply device having any one of Structures 5-3 to 5-6 described above, the controller may include the error amplifier configured to generate the error signal corresponding to the difference between the voltage corresponding to the output voltage and the reference voltage, the comparator configured to compare the slope voltage with the error signal so as to generate the reset signal as the comparison signal, the oscillator configured to generate the set signal as the clock signal of a predetermined frequency, and the timing control circuit configured to control on and off of the first switch and on and off of the second switch in accordance with the set signal and the reset signal (Structure 5-7).

In addition, in the current mode control type switching power supply device having any one of Structures 5-1 to 5-7 described above, the second switch may be a MOS transistor, and the current sensing portion may sense the current flowing in the second switch by using the voltage between both ends of the on resistor of the MOS transistor (Structure 5-8).

In addition, among the in-vehicle equipment disclosed in this specification, the in-vehicle equipment having the fifth technical feature includes the current mode control type switching power supply device having any one of Structures 5-1 to 5-8 (Structure 5-9).

In addition, among the vehicles disclosed in this specification, the vehicle having the fifth technical feature includes the in-vehicle equipment having Structure 5-9 and a battery configured to supply electric power to the in-vehicle equipment (Structure 5-10).

INDUSTRIAL APPLICABILITY

The present invention can be used for current mode control type switching power supply devices used in various fields (such as home appliances, automobiles, and industrial machines).